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PDF AD8310 Data sheet ( Hoja de datos )
| Número de pieza | AD8310 | |
| Descripción | 95 dB Logarithmic Amplifier | |
| Fabricantes | Analog Devices | |
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Fast, Voltage-Out, DC to 440 MHz,
95 dB Logarithmic Amplifier
AD8310
FEATURES
Multistage demodulating logarithmic amplifier
Voltage output, rise time <15 ns
High current capacity: 25 mA into grounded RL
95 dB dynamic range: −91 dBV to +4 dBV
Single supply of 2.7 V min at 8 mA typ
DC to 440 MHz operation, ±0.4 dB linearity
Slope of +24 mV/dB, intercept of −108 dBV
Highly stable scaling over temperature
Fully differential dc-coupled signal path
100 ns power-up time, 1 mA sleep current
APPLICATIONS
Conversion of signal level to decibel form
Transmitter antenna power measurement
Receiver signal strength indication (RSSI)
Low cost radar and sonar signal processing
Network and spectrum analyzers
Signal-level determination down to 20 Hz
True-decibel ac mode for multimeters
FUNCTIONAL BLOCK DIAGRAM
SUPPLY
+INPUT
–INPUT
COMMON
VPOS
5 8mA
BAND GAP REFERENCE
AND BIASING
AD8310
ENBL 7 ENABLE
INHI
8
1.0kΩ
1 INLO
3
SIX 14.3dB 900MHz
AMPLIFIER STAGES
MIRROR
2μA
/dB
NINE DETECTOR CELLS
SPACED 14.3dB
2 COMM
2 3kΩ
COMM
BFIN 6 BUFFER
INPUT
+ VOUT
4 OUTPUT
–
3kΩ
1kΩ
INPUT-OFFSET
COMPENSATION LOOP
COMM
OFLT 3 OFFSET
33pF
FILTER
COMM
Figure 1.
GENERAL DESCRIPTION
The AD8310 is a complete, dc to 440 MHz demodulating
logarithmic amplifier (log amp) with a very fast voltage mode
output, capable of driving up to 25 mA into a grounded load in
under 15 ns. It uses the progressive compression (successive
detection) technique to provide a dynamic range of up to 95 dB
to ±3 dB law conformance or 90 dB to a ±1 dB error bound up
to 100 MHz. It is extremely stable and easy to use, requiring no
significant external components. A single-supply voltage of
2.7 V to 5.5 V at 8 mA is needed, corresponding to a power
consumption of only 24 mW at 3 V. A fast-acting CMOS-
compatible enable pin is provided.
Each of the six cascaded amplifier/limiter cells has a small-
signal gain of 14.3 dB, with a −3 dB bandwidth of 900 MHz.
A total of nine detector cells are used to provide a dynamic
range that extends from −91 dBV (where 0 dBV is defined as
the amplitude of a 1 V rms sine wave), an amplitude of about
±40 μV, up to +4 dBV (or ±2.2 V). The demodulated output
is accurately scaled, with a log slope of 24 mV/dB and an
intercept of −108 dBV. The scaling parameters are supply-
and temperature-independent.
The fully differential input offers a moderately high impedance
(1 kΩ in parallel with about 1 pF). A simple network can match
the input to 50 Ω and provide a power sensitivity of −78 dBm to
+17 dBm. The logarithmic linearity is typically within ±0.4 dB
up to 100 MHz over the central portion of the range, but it is
somewhat greater at 440 MHz. There is no minimum frequency
limit; the AD8310 can be used down to low audio frequencies.
Special filtering features are provided to support this wide range.
The output voltage runs from a noise-limited lower boundary of
400 mV to an upper limit within 200 mV of the supply voltage
for light loads. The slope and intercept can be readily altered
using external resistors. The output is tolerant of a wide variety
of load conditions and is stable with capacitive loads of 100 pF.
The AD8310 provides a unique combination of low cost, small
size, low power consumption, high accuracy and stability, high
dynamic range, a frequency range encompassing audio to UHF,
fast response time, and good load-driving capabilities, making
this product useful in numerous applications that require the
reduction of a signal to its decibel equivalent.
The AD8310 is available in the industrial temperature range of
−40°C to +85°C in an 8-lead MSOP package.
Rev. F
Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarksandregisteredtrademarksarethepropertyoftheirrespectiveowners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
www.analog.com
Fax: 781.461.3113 ©2005–2010 Analog Devices, Inc. All rights reserved.
1 page  
AD8310
ABSOLUTE MAXIMUM RATINGS
Table 2.
Parameter
Rating
Supply Voltage, VS
Input Power (re 50 Ω), Single-Ended
7.5 V
18 dBm
Differential Drive
22 dBm
Internal Power Dissipation
200 mW
θJA
Maximum Junction Temperature
Operating Temperature Range
Storage Temperature Range
Lead Temperature (Soldering 60 sec)
200°C/W
125°C
−40°C to +85°C
−65°C to +150°C
300°C
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
ESD CAUTION
Rev. F | Page 4 of 24
5 Page 
AD8310
SLOPE AND INTERCEPT CALIBRATION
All monolithic log amps from Analog Devices use precision
design techniques to control the logarithmic slope and
intercept. The primary source of this calibration is a pair of
accurate voltage references that provide supply- and
temperature-independent scaling. The slope is set to 24 mV/dB
by the bias chosen for the detector cells and the subsequent gain
of the postdetector output interface. With this slope, the full
95 dB dynamic range can be easily accommodated within the
output swing capacity, when operating from a 2.7 V supply.
Intercept positioning at −108 dBV (−95 dBm re 50 Ω) has
likewise been chosen to provide an output centered in the
available voltage range.
Precise control of the slope and intercept results in a log amp
with stable scaling parameters, making it a true measurement
device as, for example, a calibrated received signal strength
indicator (RSSI). In this application, the input waveform is
invariably sinusoidal. The input level is correctly specified in
dBV. It can alternatively be stated as an equivalent power, in
dBm, but in this case, it is necessary to specify the impedance in
which this power is presumed to be measured. In RF practice, it
is common to assume a reference impedance of 50 Ω, in which
0 dBm (1 mW) corresponds to a sinusoidal amplitude of
316.2 mV (223.6 mV rms). However, the power metric is
correct only when the input impedance is lowered to 50 Ω,
either by a termination resistor added across INHI and INLO,
or by the use of a narrow-band matching network.
Note that log amps do not inherently respond to power, but to
the voltage applied to their input. The AD8310 presents a
nominal input impedance much higher than 50 Ω (typically
1 kΩ at low frequencies). A simple input matching network
can considerably improve the power sensitivity of this type of
log amp. This increases the voltage applied to the input and,
therefore, alters the intercept. For a 50 Ω reactive match, the
voltage gain is about 4.8, and the whole dynamic range moves
down by 13.6 dB. The effective intercept is a function of wave-
form. For example, a square-wave input reads 6 dB higher than
a sine wave of the same amplitude, and a Gaussian noise input
reads 0.5 dB higher than a sine wave of the same rms value.
OFFSET CONTROL
In a monolithic log amp, direct coupling is used between the
stages for several reasons. First, it avoids the need for coupling
capacitors, which typically have a chip area at least as large as
that of a basic gain cell, considerably increasing die size. Second,
the capacitor values predetermine the lowest frequency at which
the log amp can operate. For moderate values, this can be as
high as 30 MHz, limiting the application range. Third, the
parasitic back-plate capacitance lowers the bandwidth of the
cell, further limiting the scope of applications.
However, the very high dc gain of a direct-coupled amplifier
raises a practical issue. An offset voltage in the early stages of
the chain is indistinguishable from a real signal. If it were as
high as 400 μV, it would be 18 dB larger than the smallest ac
signal (50 μV), potentially reducing the dynamic range by this
amount. This problem can be averted by using a global feedback
path from the last stage to the first, which corrects this offset in
a similar fashion to the dc negative feedback applied around an
op amp. The high frequency components of the feedback signal
must, of course, be removed to prevent a reduction of the HF
gain in the forward path.
An on-chip filter capacitor of 33 pF provides sufficient suppres-
sion of HF feedback to allow operation above 1 MHz. The −3 dB
point in the high-pass response is at 2 MHz, but the usable range
extends well below this frequency. To further lower the frequency
range, an external capacitor can be added at OFLT (Pin 3). For
example, 300 pF lowers it by a factor of 10.
Operation at low audio frequencies requires a capacitor of about
1 μF. Note that this filter has no effect for input levels well above
the offset voltage, where the frequency range would extend
down to dc (for a signal applied directly to the input pins). The
dc offset can optionally be nulled by adjusting the voltage on
the OFLT pin (see the Applications Information section).
Rev. F | Page 10 of 24
11 Page | ||
| Páginas | Total 25 Páginas | |
| PDF Descargar | [ Datasheet AD8310.PDF ] | |
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